Read about partial S2p measurement, and learn why you need it and how to make this improved measurement.
In the design or optimisation of a voltage regulation module (VRM), its output impedance data and impedance data for the filter inductors and capacitors are necessary to have complete simulation models. Unfortunately, vendor data on these components is often incomplete, erroneous, or difficult to decipher in terms of the setup involved to make the measurement. Thus, we often need to collect the data ourselves.
The measurements need to be performed over the entire frequency range of interest, typically from a few kiloHertz to about 1GHz, depending on the application. Because of this very wide frequency range, we generally turn to S-parameter based measurements. High performance simulators can directly incorporate the S-parameter component measurements in AC, DC, transient, and harmonic balance simulations while including the finite element PCB models.
While extremely useful, standard S-parameter measurements frequently aren't sufficient. What's really needed is an extended range, that is, a partial S2p measurement. I'll explain why you need it and how to make this improved measurement.
S-parameters are a simple method of performing measurements over a very wide frequency range. The measurement is performed using a fixed resistance port rather than a high impedance probe. Two options are available for measuring impedance with S-parameters. One option is a reflection measurement and the other option is THRU measurement.
One port or two? Why partial?
The reflection, or 1-port, measurement is the simplest because it requires only one cable. But, it also requires a complex calibration, generally consisting of an OPEN calibration, a SHORT calibration, and a LOAD or MATCH calibration of the port used for the measurement. Most VNA's (vector network analysers) include the transformation from the S-parameter reflection measurement (S11 or S22) to impedance, but it's quite simple. Using port 1 as an example, the reflection for a given reference impedance, Zref, (typically 50 Ω) the relationship between S11 and the device impedance is shown in table 1.
Table 1: 1-Port transformations.
We can perform a 2-port measurement by placing the device to be measured either in series with or in shunt with the measurement ports. Table 2 shows the relationship between S21 and the device impedance for both the series and shunt configuration.
Table 2: 2-Port transformations.
DC ground loop
An additional issue arises for the 2-port shunt-thru measurement due to a DC ground loop, which occurs as a result of the RF ground at the VNA and the series resistance of the interconnecting measurement cables. The Keysight E5061B VNA has a semi-floating input on the low frequency gain-phase ports, eliminating this DC ground loop for low impedance measurements up to 30MHz. For the E5061B high frequency ports and other VNAs in general, the DC ground loop must be minimised using a common-mode coaxial transformer such as the Picotest J2102A. Otherwise, the low frequency measurements will be inaccurate. The setup diagrams for these impedance measurement options are shown in figure 1.
Figure 1: Basic schematics for the 1-port and 2-port impedance measurements.
The simulations in figure 2 show the S-parameter magnitude for each measurement technique as a function of the device impedance. All measurements lose sensitivity as the S-parameter magnitude approaches 1.0
Figure 2: S-parameter magnitude as a function of the device impedance.
Figure 3 shows a higher resolution view of the S parameter magnitude from 0.95 to 1.0.
Figure 3: Higher resolution view of the S-parameter magnitude as a function of the device impedance.
Setting the measurable S-parameter (either S11, S22 or S21) to a minimum of 40E-6 allows for a reasonable signal-to-noise margin and a maximum of 0.95. The ranges for each measurement are shown in table 3.
Table 3: Measurement Impedance ranges.
Which range do we need?
Because we're typically measuring VRMs, PDN's (power distribution networks), capacitors, and inductors, the minimum impedance measurement is in the milliOhms range—whether it is inductor DCR (DC resistance), VRM output impedance, or capacitor ESR (equivalent series resistance). This requires the 2-port shunt measurement. The measured S-parameter file must be valid for the complete simulation frequency range. Establishing the measurement range to be from 1kHz to 500MHz and using what I call the "realistic measurement range," we can determine the maximum inductance or capacitance that can be measured using the 2-port shunt measurement. Using the 2-port shunt measurement, the minimum capacitance that can be measured is 800 nF, precluding the measurement of high-frequency decoupling capacitors. The maximum inductance that can be measured at 500MHz is only 60 nH. Even if the inductor is assumed to have a resonant frequency of 100MHz, the maximum inductance that can be measured is less than 1µH, precluding the measurement of ferrite beads and most output filter inductors. Another issue arises in making this measurement. S21, S11, and S22 are all measuring the same device and therefore the same impedance range. As explained above, the S11 and S22 measurements fall below the range of the 1-port measurement. For example, while measuring an inductor, the DCR will be measured as S11 and S22. While measuring a capacitor, the ESR will be measured using S11 and S22. These 1-port terms will be invalid at low impedance levels typical of the devices. That's why we need a "partial" 2-port thru measurement. We will only keep the S21 term and remove the S11 and S22 terms because they're invalid at impedance levels below 0.5 Ω. Some instruments allow saving the measurement as a Touchstone impedance file, which is a partial 2-port s-parameter file.
Extending the 2-port range
We can scale the measurement using series resistors, effectively increasing the port's reference impedance. That lets us measure the decoupling capacitors and larger inductors. Figure 4 shows the results of this measurement.
Figure 4: Adding series resistors to extend the impedance range of the 2-port shunt measurement.
For example, adding a 450 Ω series resistor makes the reference impedance 500 Ω, shifting the measurement range up by a factor of 10. In some cases, the added series resistors can be accommodated by using an attenuating transmission line oscilloscope probe. Scaling factors of 1, 5, 10 and 20 are commercially available as 1-port probes. A pair of probes can be used to make a 2-port extended range measurement. The measurement range for various values of series resistors are shown in table 4.
Table 4: Measurement Impedance ranges for various series resistor values.
The impedance transformation with the series resistors included is shown in table 5.
Table 5: Impedance transformation including series resistors.
For measurements at either extreme of the measurement range, be sure to perform a full fixture removal calibration or full 1 port calibration on both parts as well as a THRU calibration. If series resistors are included, perform the THRU calibration with the series resistors included in the setup. A 0.1µF ceramic capacitor is used as an example of the extended range two port impedance measurement. The results are shown up to 30MHz in figure 5. The impedance measurement spans the range of more than 1 kΩ and below the 9 mΩ ESR.
Figure 5: Measurement of a 0.1µF capacitor with RS=200 Ω.
Higher frequency, low impedance measurements are very sensitive to even very small fixture inductance and at high frequency, high impedance measurements are very sensitive to even very small fixture capacitance. A smaller, 1 nF capacitor can eb measured at frequencies up to 1GHz. Figure 6 shows the results.
Figure 6: The plot shows a measurement of of a 1 nF capacitor at frequenies up to 1GHz. The resonance results from the capacitor ESL combined with the SMA connector capacitance of approximately 1 pF.
The 850MHz resonance is the result of approximately 1 pF of excess capacitance from the low-quality SMA connectors. To accurately measure at these frequencies, we need better connectors and/or the excess capacitance needs to be calibrated out of the measurement.
The extended range technique and saving the S21 data only or a Touchstone Z data file provides a method of scaling the measurement to optimise the measurement window. Added benefits are that the extension resistors reduce the loading when measuring lower power VRM's. This technique can also be used for measuring the output impedance of voltage references and closed loop op-amps and is supported by the Picotest non-invasive stability measurement as well.
About the author
Steve Sandler is the managing director of Picotest.